Dynamic bias controller for power amplifier circuits

ABSTRACT

A bias controller sets the quiescent current of a power amplifier to a desired value by dynamically adjusting the power amplifier bias voltage. Using closed-loop control, the bias controller sets the bias voltage to whatever value is needed despite circuit component variations and temperature effects. Operation of the bias controller complements dynamic bias voltage adjustment in advance of transmit operations, such as in advance of a transmit burst. In a first state, where the power amplifier is in a quiescent condition, the bias controller adjusts bias voltage to set the desired quiescent current by detecting the supply current into the power amplifier. The bias controller then transitions to a second state, where it maintains the adjusted bias voltage irrespective of amplifier supply current. Despite its ability to sense supply current into the power amplifier, the bias controller&#39;s configurations avoid dissipative current sensing during normal operation of the power amplifier.

BACKGROUND OF THE INVENTION

[0001] Wireless communication devices are an integral part of modernexistence, with a wide range of different device types in use,including, but not limited to, cellular telephones, portable digitalassistants, wireless-enabled computers, and other so-called “pervasivecomputing” devices. While the use and capability of these devices varyconsiderably, each includes one or more of the fundamental buildingblocks comprising essentially any wireless communication device.

[0002] For example, any wireless device capable of transmitting a radiofrequency (RF) signal includes some form of transmitter circuit totransmit a RF signal in accordance with a defined modulation scheme.Power amplification is a fundamental part of this signal transmissioncapability. Typically, the desired transmit signal is formed at arelatively low power level, and this pre-amplified signal is thenamplified by a RF power amplifier, which boosts the signal power to alevel suitable for radio transmission. Oftentimes, the level of transmitpower is tightly controlled, such as in cellular telephony.

[0003] Controlling the output power of a RF power amplifier requiresaccurate control of the amplifier's bias voltage. That is, essentiallyall power amplifier circuits are implemented as transistor-basedamplifiers, whether single- or multi-stage, and control of output powerfrom these transistor-based amplifiers requires accurate control oftransistor operating points.

[0004] Generally, an applied bias voltage establishes the operatingpoint of a power amplifier. Indeed, operating point control affectswhether the transistor operates in a linear or in a saturated mode, andgreatly affects the amplification efficiency of the power amplifier,which is a dominant influence on battery life in portable wirelessdevices. Nominally, a given magnitude of bias voltage corresponds to agiven level of quiescent current in the power amplifier, which currentis determinative in setting the eventual output power of the poweramplifier when stimulated with an RF source at its input. Ideally, onewould simply set the bias voltage to the nominal level corresponding tothe desired quiescent current. Unfortunately, a host of variables,including semiconductor process variations, temperature, aging,operating voltages, and others conspire to alter the relationshipbetween a given bias voltage and the resultant amplifier quiescentcurrent. In other words, one cannot simply choose the bias voltage thatshould result in the desired quiescent current; instead, one generallyneeds to adopt some form of bias voltage calibration or adjustment.

[0005] Of course, these calibration approaches add expense andcomplication, particularly on the manufacturing side where, in somecases, individual power amplifier circuits (or whole communicationdevices) are characterized over temperature and voltage to determineappropriate adjustment factors for bias voltage. This calibrationinformation generally is then loaded into non-volatile memory within thecalibrated devices for use in later operation.

BRIEF SUMMARY OF THE INVENTION

[0006] The present invention provides a method and apparatus fordynamically calibrating voltage bias into a power amplifier circuit inadvance of transmit operations to ensure that the power amplifiercircuit is biased to a desired quiescent current level. Although subjectto implementation variations in many different embodiments, the presentinvention generally provides a bias controller that uses closed-loopcontrol techniques to adjust a generated bias voltage up or down to makethe supply current into the power amplifier circuit under quiescentconditions substantially match the target quiescent current value.

[0007] A timing function, which may be included in the bias controller,controls first and second operating states for the bias controller.During the first operating state, the bias controller adjusts biasvoltage under closed-loop control based on measured or detected supplycurrent into the power amplifier circuit. Thus, during the first state,the bias controller uses closed-loop control to adjust the bias voltageto whatever level is needed to achieve the target level of quiescentcurrent. After some defined duration, the bias controller transitionsfrom its first state to its second state, at which point it locks orotherwise holds the adjusted level of bias voltage irrespective of anychanges in the supply current into the power amplifier circuit.

[0008] In operation, the first state is made to occur during quiescentconditions of the power amplifier circuit, such as before a radiotransmit burst. As the bias controller transitions from its first to itssecond state, it locks or holds the adjusted bias voltage and maintainsthis bias voltage value through any subsequent radio transmissions.

[0009] In some exemplary embodiments, the bias controller is configuredwith a measurement path for measuring supply current into the poweramplifier circuit that is independent of the primary path that providessupply current to the power amplifier circuit during transmitoperations. In this manner, the bias controller avoids loading theprimary supply path with any current measurement devices it might use tosense supply current into the power amplifier during bias voltageadjustment operations.

[0010] In other exemplary embodiments, the bias controller may use areference current that has some defined proportionality to the actualsupply current. Such reference currents are sometimes used in currentmodulators used in envelope-elimination-and-restoration (EER)applications. In EER systems, which are also referred to as “polar”modulation systems, the power amplifier is biased for saturated modeoperation. A constant-envelope, phase-modulated signal is applied to theamplification input of the power amplifier, while its supply terminal issupplied with amplitude modulated supply voltage and/or current. Wherecurrent modulation is used, the bias controller may use a referencecurrent generated as a scaled reference of the modulated supply current.

[0011] With this approach, the bias voltage adjustment control loop maybe closed based on sensing the reference current rather than the actualcurrent. Again, this approach avoids placing dissipative components inthe supply current path of the power amplifier. During its first stateof operation, amplitude modulation of the supply and reference currentsis suspended, and no RF signal is applied to the power amplifier. Thebias controller may include switching elements for isolating the currentmodulator from any input modulation signals to force this quiescentcondition during the bias controller's adjustment operations.

[0012] Regardless of the its particular implementation, the biascontroller's closed-loop adjustment approach accommodates variations inthe relationship between supplied bias voltage and resultant quiescentcurrent, thereby eliminating the need for stored calibrationinformation, and any temperature- or voltage-based bias adjustmenttracking. That is, with the bias controller of the present invention,the bias voltage is adjusted under closed-loop control to whatever valueis needed to fix the quiescent supply current of the power amplifiercircuit at the target value.

[0013] Generally, the bias controller includes accommodations to ensurethat the supply voltage applied to the power amplifier circuit duringits bias voltage adjustment operations is of sufficient magnitude toreliably set the quiescent current level. That is, with some amplifiertypes, such as with bipolar junction transistor amplifiers, an adequatevoltage between the collector and emitter, is required to reliably setthe quiescent current level. Field effect transistors (FETs) typicallyhave corresponding drain-to-source voltage ranges that should bemaintained while setting bias voltage. Further, the bias controlleroperates to ensure that any voltage differences between the first state(adjustment) and the second state (transmit operations) are not sosubstantial that errors would result in the quiescent current levelbetween the two operating states.

BRIEF DESCRIPTION OF THE DRAWINGS

[0014]FIG. 1 is a diagram of a conventional wireless communicationdevice employing stored calibration information to effect amplifier biasvoltage control.

[0015]FIG. 2 is a graph illustrating the generalized relationshipbetween transistor amplifier operating point and input/output RF power.

[0016]FIG. 3 is a diagram of a single-stage transistor amplifier subjectto bias voltage control.

[0017]FIG. 4 is a diagram of an exemplary communication deviceincorporating a bias controller according to the present invention.

[0018]FIG. 5 is a diagram of exemplary details for one embodiment of thebias controller.

[0019]FIG. 6 is a diagram of another embodiment of the bias controllerconfigured to operate in conjunction with a current modulator.

[0020]FIG. 7A is a diagram of exemplary details for the bias controllerand current modulator of FIG. 6, while FIG. 7B illustrates exemplarycontrol waveforms associated with timing the operation of the biascontroller and current modulator.

[0021]FIG. 8 is a graph of exemplary bias adjustment timing in a radiotransmit burst environment, such as that employed in by the GSMcommunication standards.

[0022]FIG. 9 is graph of alternate bias adjustment timing relative tothe burst transmission.

[0023]FIG. 10 is a diagram of another embodiment of the bias controllerand current modulator where the power amplifier supply voltage usedduring bias voltage adjustment is independent of the primary supplyvoltage used during transmit operations.

[0024]FIG. 11 is a diagram of another embodiment of the bias controllerand current modulator where the supply voltage limit is detected and fedto the baseband processor, which then adjusts V_(IDQREF) to compensatefor battery voltage variation.

DETAILED DESCRIPTION OF THE INVENTION

[0025]FIG. 1 illustrates an approach to power amplifier biasing as mightbe used in a conventional wireless communication device 10. The device10 comprises a transceiver 12, which cooperates with a digital signalprocessor (DSP) 14 to process a received signal from an antenna assembly16 after filtering and conditioning by a filter circuit 18. Thetransceiver 12 also cooperates with the DSP 14 to produce a transmitsignal which is input to a power amplifier 20. Amplification of thetransmit signal by the power amplifier 20 generates an RF output signalsuitable for transmission by antenna assembly 16. An impedance matchingcircuit 22 may be used to couple the RF output signal from the poweramplifier 20 to the antenna assembly 16.

[0026] Commonly, the device 10 is required to transmit its RF outputsignal at a specified transmit power, or at least within a specifiedrange of output powers. The RF output power achievable with a typicalpower amplifier is determined by its operating point. FIG. 2 is ageneric graph of the relationship between input RF power and output RFpower as a function of power amplifier operating point. Bias control isused to establish the operating point of a power amplifier, and FIG. 3illustrates a typical power amplifier circuit arrangement and themechanism for receiving a bias voltage signal.

[0027] For simplification, power amplifier 20 is illustrated as a singlestage transistor amplifier comprising transistor Q1 having its collectortied to an input supply terminal 34 which is coupled to a supply voltageV_(DD) through an inductor L1, an emitter tied to signal ground throughterminal 36, and a base coupled through R1 to a bias voltage applied toterminal 38. The base is also AC-coupled through capacitor Cl to an RFinput signal applied to terminal 30.

[0028] In operation, a bias voltage is applied to terminal 38 toestablish a quiescent current into the collector of transistor amplifierQ1, thereby establishing the transistor operating point. Application ofthe RF input signal causes the transistor Q1 to begin self-biasing, butnonetheless the average bias point is maintained by the bias voltageV_(BIAS).

[0029] One of the difficulties encountered in proper power amplifierbiasing arises from the uncertainties in the relationship between agiven bias voltage and a resultant quiescent current. That is, the samebias voltage applied to different specimens of the same type of poweramplifier circuit, or applied to the same amplifier at differenttemperatures produces varying quiescent currents. Table 1 belowillustrates output power sensitivity relative to amplifier quiescentcurrent for a typical RF power amplifier. TABLE 1 TYPICAL LINEAR PASPECIFICATIONS PARAMETER MIN TYP MAX PWR GAIN 28 dB 31 dB 34 dB I_(DQ)50 mA 100 mA 300 mA ACPR 26 dBc 29 dBc 32 dBc

[0030] As seen from the table data, power gains in a typical poweramplifier vary significantly with changes in quiescent current I_(DQ).Moreover, differing quiescent currents varies the operating point of thepower amplifier, causing changes in its amplification characteristics(e.g., linearity), which influences the adjacent channel power ratio(ACPR) performance of the power amplifier. ACPR performance is importantbecause of the need to minimize cross-channel interference between theclosely spaced communication channel frequencies in a typical wirelesscommunication system.

[0031] With the above voltage biasing problems in mind, the reader isreferred back to FIG. 1 for an understanding of how these difficultiesare addressed in the conventional device 10. In the illustration, onesees that the DSP 14 has access to a look-up table (LUT) or some othersimilar data structure implemented in a memory 24. Data stored in memory24 comprise calibration information for needed variations or adjustmentsof power amplifier bias voltage over temperature, and potentially overtime (e.g., drifting due to component aging), and may include multiplesets of data for different operating points, corresponding to differentmodes of device operation. Indeed, the overall set of variables thatinfluence the resultant quiescent current for a given bias voltage valueare complex enough that individualized calibration data is oftencollected and stored for each device 10. In any case, an undesirableamount of time and labor is expended, often on a per-unit basis, tocharacterize and store the needed calibration data in memory 24.

[0032]FIG. 4 illustrates an exemplary communication device 50 accordingto the present invention. Here, the communication device 50 includes anexemplary bias controller 52, which comprises a supply current detectioncircuit 54, and a closed-loop control circuit 56. Device 50 furtherincludes a power amplifier 60, impedance matching network 62, antennaassembly 64, transceiver 66, and baseband processor 68.

[0033] In operation, bias controller 52 supplies power amplifier 60 witha bias voltage adjusted to set the quiescent current of power amplifier60 to a desired quiescent current value. Bias voltage adjustmentoperations of the bias controller 52 are controlled relative to thetransmit operations of device 50, such that bias voltage adjustment isperformed under quiescent conditions of the power amplifier 60.

[0034] Power amplifier 60 generates a RF output signal (RF_OUT)responsive to an RF input signal (RF_IN) from transceiver 66. The RF_OUTsignal is coupled to antenna assembly 64 through the impedance matchingnetwork 62, where it is radiated outward as a transmitted signal. Theradio transceiver 66 cooperates with baseband processor 68 to generatethe RF_IN signal according to desired transmit information, and inaccordance with applicable modulation protocols (e.g., IS-136, GSM, orother wireless communication standards).

[0035] In terms of bias control, baseband processor 68 cooperates withthe bias controller 52 to achieve an adjusted bias voltage level thatsets the quiescent current into the power amplifier 60 at a desiredtarget value. In this embodiment, the baseband processor 68 generates,or otherwise controls, a reference voltage V_(IDQREF) that isproportionately representative of the desired quiescent current value.Thus, the baseband processor, which may include digital analogconversion facilities, controls the magnitude of V_(IDQREF) inaccordance with the desired quiescent current value. Bias controller 52uses closed-loop control responsive to V_(IDQREF) and the measuredsupply current (I_(PA)) into the power amplifier 60 to set the quiescentcurrent level of I_(PA). Once the appropriate adjustment for the biasvoltage V_(BIAS) is obtained, the bias controller 52 holds this voltageconstant irrespective of any subsequent change in supply current intothe power amplifier 60.

[0036] More particularly, the bias controller 52 operates in a firststate where it dynamically adjusts the bias voltage V_(BIAS) to achievethe desired quiescent current value for the power amplifier supplycurrent I_(PA), and then transitions into a second state where it holdsor otherwise maintains the adjusted level of V_(BIAS) irrespective ofchanges in I_(PA). Transitioning between the first and second states ofoperation for the bias controller 52 is controlled by enable signal (EN)generated by the baseband processor 68. As will be explained in moredetail later, the baseband processor 68 typically asserts the enablesignal in advance of radio transmit activity. That is, the EN signal isgenerally asserted before transmit operations, with the power amplifierheld at quiescent conditions (with no applied RF power). The timingfunction within the bias controller 52 converts the enable signal into ashorter duration control pulse. While the control pulse is asserted, thebias controller 52 operates in the first state by applying closed-loopadjustment to V_(BIAS) to achieve the desired quiescent current value ofI_(PA), and upon de-assertion of the pulse, it transitions to the secondstate where it holds the adjusted level of V_(BIAS).

[0037]FIG. 5 illustrates details for an exemplary embodiment of the biascontroller 52. Here, the closed-loop control circuit 56 comprises anamplifier circuit 80 and a track-and-hold circuit 82. The amplifiercircuit 80 generates an error signal based on a difference betweenV_(IDQREF) and the detection signal provided by the current detector 54.In this embodiment, the detection circuit 54 comprises a sense resistorR_(Q) disposed in series in a measurement path that selectively couplesthe supply input of the power amplifier 60 to the supply voltage V_(DD)through operation of a switch 84. While switch 84 is drawn as asingle-pole, double-throw (SPDT) switch, it should be understood thatits implementation might involve the use of separate switches. In anycase, supply current I_(PA) to power amplifier 60 may be selectivelyconducted through either the measurement path or through a primary pathby operation of switch 84, which might comprise discrete field effecttransistors (FET) disposed in series in the primary and measurementpaths.

[0038] Regardless of the particular approach taken for selectivelyenabling the measurement and primary paths, the measurement path isswitched in during the adjustment period of operation for the biascontroller 52. That is, supply current I_(PA) to the power amplifier 60flows through the measurement path and therefore flows through the senseresistor R_(Q) during the adjustment period. Consequently, the detectionsignal represents a voltage signal that is below the supply voltageV_(DD) by an amount proportionate to the magnitude of supply currentI_(PA) flowing into the power amplifier 60 because of the voltage dropcaused by that current across the sense resistor R_(Q). In this manner,the error signal is responsive to the actual level of quiescent currentflowing into the power amplifier 60 compared to the desired or targetquiescent current value.

[0039] A pulse generator 86, which may be a one-shot device, generatesthe bias calibration control pulse, here labeled as QCHK that drives thepath selection switch 84 and the track-and-hold circuit 82. Operation ofthe track-and-hold circuit 82 in response to the QCHK signal isdiscussed below.

[0040] When the enable signal is asserted, the pulse generator 86asserts QCHK for a defined period. While QCHK is asserted, thetrack-and-hold circuit 82 operates in a tracking mode, and varies thegenerated bias voltage V_(BIAS) as a function of the error signal outputby the amplifier circuit 80. Thus, the bias voltage V_(BIAS) trackschanges in the error signal during the first state of operation toprovide closed-loop adjustment of V_(BIAS). Because the magnitude of thebias voltage V_(BIAS) controls the magnitude of supply current I_(PA)into the power amplifier 60, a closed-loop control mechanism isestablished whereby amplifier circuit 80 drives the error signal eitherup or down such that the bias voltage V_(BIAS) moves either up or downto minimize the difference between the detection signal and V_(IDQREF).Thus, while in its first state of operation, the bias controller 52 setsthe bias voltage V_(BIAS) to whatever level is needed to achieve thedesired or target quiescent current value for supply current I_(PA) asrepresented by the reference voltage V_(IDQREF).

[0041] At the conclusion of the defined period, control signal QCHK isde-asserted, and the tracking circuit 82 transitions to its second statewhere it holds the adjusted level of the bias voltage V_(BIAS).Additionally, switch 84 changes state, thereby coupling the supply inputof the power amplifier to the supply voltage V_(DD) through the primarypath, thus avoiding the need for sourcing supply current I_(PA) throughsense resistor R_(Q) during normal transmit operations of poweramplifier 60.

[0042] At this point, the current flowing through the sense resistorR_(Q) goes to zero and the detection signal rises to the level of thesupply voltage V_(DD). While this change in the detection signal causesa potentially large change in the error signal generated by theamplifier circuit 80, the track-and-hold circuit 82 ignores changes inthe error signal. Bias voltage V_(BIAS) is thus maintained at thepreviously adjusted level irrespective of changes in the actual supplycurrent I_(PA) into the power amplifier 60. In this second state, RFinput power may be applied to the power amplifier 60 withoutupsetting-or otherwise changing the level of bias voltage provided bythe bias controller 52.

[0043] While it was generally assumed in the preceding discussion thatthe bias controller 52 provided bias voltage to establish a linear pointof operation for the power amplifier 60, linear operation is notnecessary or even desirable in some applications. FIG. 6 illustrates thepower amplifier circuit 60 configured for use in anenvelope-elimination-and-restoration (EER) application. Here, the poweramplifier circuit 60 is operated as a saturated mode amplifier, and thebaseband processor 68 generates separate phase and amplitude modulationwaveforms. Thus, the RF_IN signal to the power amplifier 60 comprises aconstant envelope phase modulation signal, while the power supply signalfrom an AM modulator 90 comprises a supply current modulated inaccordance with a desired modulation signal AM_IN. Consequently, the RFoutput signal RF_OUT from the power amplifier circuit contains bothphase and amplitude modulation information.

[0044] Depending upon the particular configuration of the modulator 90,the bias controller 52 may or may not use a measurement path to detectsupply current into the power amplifier circuit 60. FIG. 7A illustratesan exemplary embodiment of the modulator 90 and bias controller 52.Referring to FIG. 7B, the enable signal EN is asserted in advance oftransmit operations. Upon assertion of the EN signal, the pulsecontroller 86 of the bias controller 52 generates the QCHK controlpulse, which has a defined pulse width that is typically much less(e.g., 15 μs) than the typical width of the overall enable pulse. Uponassertion of QCHK, irrespective of whether negative or positive logicsense is used, transistor Q3 is turned on thereby enabling supplycurrent I_(PA) to flow through the measurement path which includes thesense resistor R_(Q) of detector circuit 54. Simultaneously, switch 102connects the input of differential error amplifier U₁ to ground,effectively turning off Q₁ and Q₂, and disabling the primary path. Inthis sense, transistor Q3 and switch 102 function together as theselector switch 84 shown in FIG. 5.

[0045] QCHK also drives the track-and-hold circuit 82. Morespecifically, the track-and-hold circuit 82 includes the logic inverterU3 to generate the inverse of QCHK, which inverse signal is used todrive switch 100 that couples a signal input of the track-and-holdcircuit 82 to the error signal generated by the error amplifier 80,shown here as U2. When switch 100 is closed, the error signal voltage isimpressed on capacitor C_(HOLD), which is coupled to an input of bufferamplifier U4. Thus, in this embodiment, the bias voltage V_(BIAS)represents a buffered version of the error signal voltage impressed onthe storage capacitor C_(HOLD). Thus, storage capacitor C_(HOLD)functions as an analog storage element that tracks the error signalvoltage during the time that the coupling switch 100 is closed.

[0046] At the same time, switch 102, which also forms a part of the biascontroller 52 in this embodiment, switches the input of a modulationcontrol amplifier U1 from its default connection with the amplitudemodulation signal AM_IN to its bias voltage calibration connection withground. Switching the inverting input of U1 to ground disables Q1 andQ2, thereby disabling the primary current path into the power amplifiercircuit 60, and causing all supply current I_(PA) into the poweramplifier 60 to flow through sense resistor R_(Q) during quiescentconditions, e.g., I_(PA)=I_(Q).

[0047] At the end of the QCHK control pulse, switch 102 decouples theinverting input of U1 from ground and again couples that input to theamplitude modulation signal AM_IN. Likewise, transistor Q3 shuts offthereby disabling the measurement current path. Similarly, switch 100opens, thereby placing the track- and-hold circuit 82 in its holdcondition. Note that use of the buffer amplifier U4 prevents loading ofthe storage capacitor C_(HOLD) by the bias input of power amplifier 60.That is, the very high input impedance of buffer amplifier U4, incombination with the high input impedance of the open switch 100,results in essentially no discharge of the storage capacitor C_(HOLD)between bias voltage calibration cycles.

[0048]FIG. 7B introduced the idea of synchronizing bias voltagecalibration operation of the bias controller 52 with radio transmitoperations. FIG. 8 provides considerably more detail for such animplementation in the context of a transmit burst as might be used wherethe device 50 is configured for operation in a wireless communicationsystem based on, for example, the Global Standard for MobileCommunication (GSM).

[0049] In GSM, transmit bursts consist of a burst start where thetransmit power is ramped up to a defined level; followed by a modulationperiod, and then terminated by a ramp end where the transmit power fallsoff in controlled fashion. A power mask envelope defines permissibletransmit power during these various portions of the transmit burst.

[0050] In typical operation, certain elements or circuits of thecommunication device 50 are operated in intermittent fashion relative tothe transmit bursts to save power. For example, certain portions of thetransceiver 66 and perhaps of the baseband processor 68, as well as thebias controller 52 and power amplifier 60, are operated in intermittentfashion synchronized with the required transmit burst. Thus, the enablesignal EN may be set to produce an enable pulse width that is somewhatwider than the required transmit burst width, with the initial portionof the EN signal leading the actual start of the transmit burst by adesired amount of time. Thus, the pulse controller 86 can be made togenerate a control pulse at the beginning of the much wider enablepulse. This allows the bias controller 52 to calibrate or otherwiseadjust the bias voltage V_(BIAS) to the level required to hit the targetquiescent current level for the power amplifier circuit 60, and thenlock and hold that adjusted bias voltage into and through one or moresubsequent transmit bursts.

[0051]FIG. 9 is similar to FIG. 8 but shows an alternative placement ofthe bias voltage calibration process relative to the transmit burst.Here, bias calibration is synchronized essentially with the start of thetransmit burst, such that bias voltage calibration occurs before thestart of actual RF signal modulation, but within the beginning period ofthe transmit burst. Indeed, the control pulse is configured to occur notat the very beginning of the transmit burst, but at a slightly laterpoint where the allowable transmit power as defined by the transmitpower mask is more generous with respect to radiated power from thecommunication device 50.

[0052] One reason for position adjustment operations at that point isthat as various portions of the transceiver 66 are powered up, e.g.,oscillators, etc., there may be some low-level leakage signal into theRF input of the power amplifier circuit 60. Such leakage might result ingreater than allowed RF signal power inadvertently radiating from thedevice 50 during bias voltage calibration. Thus, moving bias voltagecalibration to a point where the transmit power mask allows appreciableradiated power prevents inadvertently violating the power mask limits.

[0053]FIG. 10 illustrates an approach similar to that adopted in FIG.7A. However, in FIG. 7A the supply current for the power amplifiercircuit 60 was sourced from the same supply voltage V_(DD) during bothbias voltage calibration and during normal transmit operation. Onesubtlety associated with conducting bias voltage calibration operationsusing supply voltage V_(DD) to provide supply current I_(PA) is thatV_(DD) is often times simply the direct output of a battery. This isparticularly true where communication device 50 comprises a mobilecommunication device such as a cellular radiotelephone or other type ofmobile station. Thus, the magnitude of the supply voltage V_(DD) variesas a function of the state of charge of the battery (not shown). Asthose skilled in the art will readily appreciate, V_(DD) will exhibit adischarge curve characteristic of the particular battery technology(chemistry) used.

[0054] Generally, this poses no difficulties with regard to accuratelysetting the bias voltage to achieve the desired quiescent current level,but may be undesirable for certain types of power amplifier circuits 60,or for other reasons. In those instances, or as desired, the biascontroller 52 may be modified to operate such the supply current I_(PA)during bias adjustment operations is sourced from a different voltagesupply than that used during transmit operations.

[0055] In an exemplary approach, a reference voltage V_(QSREF) is usedto source I_(PA) during bias voltage adjustment. V_(QSREF) may be, forexample, a regulated voltage that is derived from the supply voltageV_(DD). No particular requirements dictate a specific design for thesupply voltage used during bias voltage adjustment, but it should benoted that the current sourcing capability of whatever circuit is usedto provide the reference voltage V_(QSREF) must be sufficient to allowproper bias voltage calibration. For example, depending upon the type oftransistor elements within the power amplifier circuit 60, and upon thetarget output power levels, one might expect typical quiescent currentvalues for I_(PA) to range from 100 milliamps up to and above one Ampdepending on the specific design at hand.

[0056]FIG. 11 shows yet another of the many possible approaches toaccommodating changing V_(DD) voltage in the bias voltage calibrationprocess. Here, as with FIG. 7A, the source for supply current I_(PA)into the power amplifier 60 under quiescent conditions is the samesupply voltage V_(DD) as used for normal transmit operations. However,the baseband processor 68 measures the magnitude of V_(DD) (or a scaledversion of V_(DD)) and makes any adjustments necessary to the biasvoltage reference V_(IDQREF). That is, the reference voltage V_(IDQREF)may be varied as a function of the supply voltage applied to the poweramplifier 60 during bias voltage calibration. This approach may behelpful for some types of transistor power amplifiers, where there thequiescent current for a given bias voltage depends on the applied supplyvoltage. Therefore, with this approach the baseband processor 68 adjustsV_(IDQREF) such that it is always representative of the desiredquiescent current value regardless of the changes in the supply voltageV_(DD).

[0057] In a related alternative, V_(QSREF) may be generated to have afixed nominal value, three volts for example, but made responsive tochanges in the supply voltage V_(DD). One approach would be to coupleV_(QSREF) through a voltage divider (e.g., a resistive voltage divider)such that a fraction of V_(DD) is applied to V_(QSREF). In that manner,the fractional component of V_(QSREF) determined by V_(DD) would varywith V_(DD).

[0058] Whether or not any of the above approaches, or variationsthereof, are adopted, one should ensure that the calibration supplyvoltage applied to the power amplifier 60 is sufficient to ensure properoperation. Further, if different supply voltages are used between biasvoltage calibration and normal operation, one should ensure that thecalibration supply voltage is sufficiently close to the normal supplyvoltage of the power amplifier 60 to prevent shifts in quiescent currentwhen the power amplifier 60 is switched from the calibration supplyvoltage to the normal supply voltage.

[0059] As control of the quiescent current reference voltage V_(IDQREF)is subject to several different approaches, including theV_(DD)-dependent control aspects above, so too are other aspects of biascontrol operation subject to much variation. For example, the detectioncircuit 54 may sense or otherwise measure supply current IPA flowingthrough either the measurement or primary supply paths, but also mightmeasure a reference current that is slaved or otherwise made to vary inproportion with the actual power amplifier supply current. For anexample of this, the reader is referred to the co-pending and commonlyassigned application entitled, “CURRENT MODULATOR WITH DYNAMIC AMPLIFIERIMPEDANCE COMPENSATION,” and which is incorporated herein by referencein its entirety. In the co-pending application, a reference current isheld at a known proportion to the actual power amplifier supply current,and the bias controller 52 may measure the actual power amplifier supplycurrent by sensing the magnitude of that reference current. Thoseskilled in the art will readily appreciate that measuring poweramplifier supply current for closed-loop bias voltage adjustment may beaccomplished directly or indirectly in a variety of ways.

[0060] While the above details relate to exemplary embodiments of thepresent invention, those skilled in the art will understand that it isnot limited to those details. In general, the present invention providesa bias controller that provides dynamic calibration of bias voltage toset a desired quiescent current value of power amplifier supply currentin advance of radio transmit operations. Such bias voltage adjustmentuses closed-loop control such that the bias voltage needed for thedesired quiescent current is automatically set regardless of variationsin circuit parameters or temperature, or device aging. Therefore, thepresent invention is limited only by the scope of the following claims,and the reasonable equivalents thereof.

What is claimed is:
 1. A bias controller to generate a bias voltagesignal that sets a quiescent current value of a supply current into apower amplifier circuit, the bias controller comprising: a currentdetector to generate a detection signal responsive to the supplycurrent; and a closed-loop control circuit to adjust the bias voltageresponsive to the detection signal in a first state such that supplycurrent is set substantially equal to a desired quiescent current value,and to maintain the bias voltage during a second state irrespective ofthe detection signal.
 2. The bias controller of claim 1, wherein theclosed-loop control circuit comprises: an amplifier circuit to generatean error signal responsive to a difference between the detection signaland a reference signal representative of the desired quiescent currentvalue; and a track-and-hold circuit to generate the bias voltage as afunction of the error signal in the first state, and to maintain thebias voltage irrespective of the error signal in the second state. 3.The bias controller of claim 2, wherein the track-and-hold circuitcomprises: an input storage element coupled to an output of theamplifier circuit in the first state and decoupled in the second state,such that the input storage element tracks the error signal in the firststate and holds a last value of the error signal in the second state;and a buffer amplifier coupled to the input storage element to generatethe bias voltage based on the error signal in the first state, and basedon the last value of the error signal in the second state.
 4. The biascontroller of claim 3, wherein the buffer amplifier comprises a voltagefollower circuit with a desired signal gain.
 5. The bias controller ofclaim 4, wherein the buffer amplifier comprises a unity-gain voltagefollower.
 6. The bias controller of claim 4, wherein the track-and-holdcircuit further comprises a coupling switch to selectively couple anddecouple the input storage element from the error amplifier responsiveto a bias adjust control signal.
 7. The bias controller of claim 6,wherein the input storage element comprises a capacitor coupled at afirst end to the coupling switch and to an input of the bufferamplifier, and coupled to a signal ground node at a second end, suchthat a capacitor voltage of the capacitor follows the error signal whencoupled to the error amplifier, and remains substantially at the lastvalue of the error signal when decoupled from the error amplifier. 8.The bias controller of claim 1, wherein a supply input of the poweramplifier is coupled to a first supply voltage through a measurementpath including the current detector, and to a second voltage supplythrough a primary path bypassing the current detector, and wherein thebias controller further includes at least one switch to enable themeasurement path in the first state, and to enable the primary path inthe second state.
 9. The bias controller of claim 8, wherein the firstvoltage supply is the same as the second voltage supply.
 10. The biascontroller of claim 8, wherein the first voltage supply is a regulatedvoltage supply derived from the second voltage supply.
 11. The biascontroller of claim 8, wherein at least one switch comprises a firstswitch to enable supply current flow through the measurement path in thefirst state, and to block supply current flow through the measurementpath in the second state.
 12. The bias controller of claim 11, whereinthe current detector comprises a sense resistor coupled to at a firstend to the second supply voltage, and coupled at a second end to a firstterminal of the first switch, and wherein a second terminal of the firstswitch is coupled to the supply input of the power amplifier circuit.13. The bias controller of claim 11, wherein the at least one switchfurther comprises a second switch to disable supply current flow throughthe primary path in the first state, and to enable supply current flowthrough the primary path in the second state, such that the supplycurrent into the power amplifier circuit does not flow through the senseresistor in the second state.
 14. The bias controller of claim 1,further comprising a one-shot circuit to generate a state control pulseresponsive to an enable signal, such that the bias controller operatesin the first state during assertion of the state control pulse, andoperates in the second state when the state control pulse isde-asserted.
 15. The bias controller of claim 2, wherein the closed loopcontrol circuit further comprises an adjustment circuit to adjust thereference signal dependent on changes in the supply voltage.
 16. Thebias controller of claim 15 wherein the adjustment circuit detects thesupply current and generates the reference signal responsive to thedetected supply voltage.
 17. The bias controller of claim 16 wherein theadjustment circuit comprises a digital signal processor.
 18. The biascontroller of claim 15 wherein the adjustment circuit comprises aresistive divider circuit.
 19. A current modulator comprising: an outputcircuit to modulate a supply current responsive to an amplitudemodulation signal; a bias controller comprising: a current detector togenerate a detection signal responsive to the supply current duringquiescent conditions; and a closed-loop control circuit to adjust thebias voltage responsive to the detection signal in a first state suchthat supply current is set substantially equal to a desired quiescentcurrent value, and to maintain the bias voltage during a second stateirrespective of the detection signal.
 20. The current modulator of claim19, wherein the modulation signal is inactive in the first state andactive in the second state, such that the bias controller adjusts thebias voltage in the absence of the modulation signal.
 21. The currentmodulator of claim 20, wherein the current modulator provides the supplycurrent to the power amplifier circuit as a scaled version of areference current, and wherein the current detector of the biascontroller comprises a sense resistor disposed in series in a referencecurrent path of the current modulator.
 22. The current modulator ofclaim 20, further comprising a modulation input switch that couples amodulation input of the current modulator to the modulation signal inthe second state, and to a reference voltage in the first state suchthat adjustment of the bias voltage occurs with a supply input of thepower amplifier circuit set by the reference voltage.
 23. The currentmodulator of claim 19, wherein the closed-loop control circuitcomprises: an amplifier circuit to generate an error signal responsiveto a difference between the detection signal and a reference signalrepresentative of the desired quiescent current value; and atrack-and-hold circuit to generate the bias voltage as a function of theerror signal in the first state, and to maintain the bias voltageirrespective of the error signal in the second state.
 24. The currentmodulator of claim 23 wherein the track-and-hold circuit comprises: aninput storage element coupled to an output of the amplifier circuit inthe first state and decoupled in the second state, such that the inputstorage element tracks the error signal in the first state and holds alast value of the error signal in the second state; and a bufferamplifier coupled to the input storage element to generate the biasvoltage based on the error signal in the first state, and based on thelast value of the error signal in the second state.
 25. The currentmodulator of claim 24, wherein the buffer amplifier comprises a voltagefollower circuit with a desired signal gain.
 26. The current modulatorof claim 25, wherein the buffer amplifier comprises a unity-gain voltagefollower.
 27. The current modulator of claim 25, wherein thetrack-and-hold circuit further comprises a coupling switch toselectively couple and decouple the input storage element from the erroramplifier responsive to a bias adjust control signal.
 28. The currentmodulator of claim 27, wherein the input storage element comprises acapacitor coupled at a first end to the coupling switch and to an inputof the buffer amplifier, and coupled to a signal ground node at a secondend, such that a capacitor voltage of the capacitor follows the errorsignal when coupled to the error amplifier, and remains substantially atthe last value of the error signal when decoupled from the erroramplifier.
 29. The current modulator of claim 19, wherein a supply inputof the power amplifier is coupled to a first supply voltage through ameasurement path including the current detector, and to a second voltagesupply through a primary path bypassing the current detector, andwherein the bias controller further includes at least one switch toenable the measurement path in the first state, and to enable theprimary path in the second state.
 30. The current modulator of claim 29,wherein the first voltage supply is the same as the second voltagesupply.
 31. The bias controller of claim 29, wherein the first voltagesupply is a regulated voltage supply derived from the second voltagesupply.
 32. The current modulator of claim 29, wherein at least oneswitch comprises a first switch to enable supply current flow throughthe measurement path in the first state, and to block supply currentflow through the measurement path in the second state.
 33. The currentmodulator of claim 32, wherein the current detector comprises a senseresistor coupled to at a first end to the second supply voltage, andcoupled at a second end to a first terminal of the first switch, andwherein a second terminal of the first switch is coupled to the supplyinput of the power amplifier circuit.
 34. The current modulator of claim32, wherein the at least one switch further comprises a second switch todisable supply current flow through the primary path in the first state,and to enable supply current flow through the primary path in the secondstate, such that the supply current into the power amplifier circuitdoes not flow through the sense resistor in the second state.
 35. Thecurrent modulator of claim 19, further comprising a one-shot circuit togenerate a state control pulse responsive to an enable signal, such thatthe bias controller operates in the first state during assertion of thestate control pulse, and operates in the second state when the statecontrol pulse is de-asserted.
 36. The current modulator of claim 23,wherein the closed loop control circuit further comprises an adjustmentcircuit to detect a battery voltage and to adjust the reference voltagedependent on changes in the battery voltage.
 37. The current modulatorof claim 36 wherein the adjustment circuit comprises a digital signalprocessor.
 38. The current modulator of claim 36 wherein the adjustmentcircuit comprises a resistive divider circuit.
 39. A method ofcontrolling a bias voltage signal that sets a quiescent current value ofsupply current to a power amplifier circuit, the method comprising:detecting the supply current into the power amplifier circuit in a firststate of operation; adjusting the bias voltage during the first state ofoperation until the supply current substantially equals a desiredquiescent current value; maintaining the bias voltage during a secondstate of operation irrespective of the supply current.
 40. The method ofclaim 39, wherein the first state of operation corresponds to aquiescent period of operation for the power amplifier circuit, and thesecond state of operation corresponds to an active period of operationfor the power amplifier circuit.
 41. The method of claim 39, whereindetecting the supply current into the power amplifier circuit in a firststate of operation comprises: coupling a supply input of the poweramplifier circuit to a first voltage supply through a measurement pathincluding a sense resistor; and generating a detection signalproportionate to the supply current across the sense resistor.
 42. Themethod of claim 41, wherein adjusting the bias voltage during the firststate of operation until the supply current substantially equals adesired quiescent current value comprises: generating an error signalbased on the difference between the detection signal and a referencesignal representing the desired quiescent current value; and adjustingthe bias voltage as a function of the error signal.
 43. The method ofclaim 41, further comprising coupling the supply input of the poweramplifier circuit to a second voltage supply through a primary path thatbypasses the current sensor during the second state of operation. 44.The method of claim 39, wherein the supply current is provided to thepower amplifier circuit as a scaled version of a reference current, andwherein detecting the supply current into the power amplifier circuit ina first state of operation comprises: detecting the reference current;and inferring a value of the supply current based on a known currentscaling between the reference and supply currents.
 45. The method ofclaim 44, wherein detecting the reference current comprises measuring avoltage drop across a sense resistor placed in series with the referencecurrent.
 46. The method of claim 39, further comprising applyingsubstantially the same magnitude of supply voltage to the poweramplifier circuit during the first and second states of operation toreduce quiescent current errors arising from variations in supplyvoltage between the first and second states of operation.
 47. The methodof claim 39, wherein the power amplifier circuit is a type of bipolarjunction transistor circuit having a known Vce curve, and furthercomprising applying a voltage supply having a magnitude corresponding toa relatively flat portion of the Vce curve to the power amplifiercircuit during the first state of operation.
 48. The method of claim 39,further comprising controlling the first and second states of operationsuch that the first state of operation is a first period before atransmit signal is applied to the power amplifier circuit foramplification, and the second state of operation is a second period thatincludes amplification of the transmit signal by the power amplifiercircuit.
 49. The method of claim 48, further comprising timing the firstperiod to occur in advance of a GSM transmit burst, and timing thesecond period to extend through the GSM transmit burst.
 50. The methodof claim 48, further comprising timing the first period to occur withina GSM burst time but before a pre-amplified burst signal is applied tothe power amplifier circuit for amplification.
 51. The method of claim50, wherein the first period is positioned within the GSM burst time tooccur after the initial transmit power mask level time has expired. 52.The method of claim 39, wherein adjusting the bias voltage during thefirst state of operation until the supply current substantially equals adesired quiescent current value comprises closing a control loop thatsets the bias voltage based on a difference between the supply currentand the desired quiescent current value.
 53. The method of claim 52,wherein closing a control loop comprises: generating an error signalwith a difference amplifier coupled to a reference signal representingthe desired quiescent current level, and coupled to a detection signalproportional to the supply current; and adjusting the bias voltage as afunction of the error signal.
 54. The method of claim 39, whereinmaintaining the bias voltage during a second state of operationirrespective of the detected supply current comprises storing the biasvoltage set during the first state in an analog storage element.
 55. Themethod of claim 54 further comprising adjusting the reference signal asa function of the supply voltage.
 56. The method of claim 55 whereinadjusting the reference signal as a function of the supply voltagecomprises detecting the supply voltage and adjusting the referencesignal responsive to the detected supply voltage.
 57. The method ofclaim 56 wherein detecting the supply voltage and adjusting thereference signal responsive to the detected supply voltage is performedby a digital signal processor.
 58. The method of claim 55 adjusting thereference signal as a function of the supply voltage comprises dividingthe supply voltage in a resistive divider to generate the referencesignal such that changes in the supply voltage result in correspondingchanges in the reference signal.
 59. A method of setting supply currentinto a power amplifier to a desired quiescent current value by adjustinga bias voltage applied to the power amplifier, the method comprising:generating a detection signal proportional to the supply current;adjusting the bias voltage using closed-loop control responsive to thedetection signal such that the supply current is set to the desiredquiescent current value.
 60. The method of claim 59, further comprisingdefining first and second states of operation, wherein the bias voltageis adjusted responsive to the detection signal during the first state,and held at an -adjusted value during the second state.
 61. The methodof claim 60, further comprising generating a control pulse of a definedwidth to control operation between the first and second states.
 62. Themethod of claim 61, further comprising synchronizing generation of thecontrol pulse substantially with the beginning of a transmit enablepulse, such that the first state transpires under quiescent conditionsof the power amplifier in advance of a transmit burst, and transition tothe second state occurs in advance of the transmit burst.
 63. The methodof claim 60, further comprising adjusting the reference signal duringthe second state such that the bias voltage is responsive to changes inthe reference signal.
 64. The method of claim 59, further comprisingadjusting a nominal value of the reference signal in dependence on amagnitude of a supply voltage applied to the power amplifier duringtransmit operations.
 65. The method of claim 64, wherein adjusting anominal value of the reference signal in dependence on a magnitude of asupply voltage applied to the power amplifier during transmit operationscomprises: measuring the supply voltage; and adjusting the nominal valueof the reference signal responsive to changes in the supply voltage.